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1 - and 2 - axis magnetic sensor s hmc1001/1002/1021/1022 the honeywell hmc100x and hmc102x magnetic sensors a re one and t wo - axis surface mount sensor s d esigned for low field magnetic sensing. by addin g supporting signal processing, cost effective magne tometer s or compassing solution s are enabled. th e s e small , low cost solution s are easy to assemble for high volume oem designs. applications for the hmc100x and hmc102x sensors include compassing, navigation systems, magnetometry, and current sensing. the hmc100x and hmc102x sensors utilize honeywell?s anisotropic magnetoresistive (amr) technology that provides advantages over coil based magnetic sensors. they are extremely sensitive, low field, solid - state magnetic sensors designed to measure direction an d magnitude of earth?s magnetic fields, from tens of micro - gauss to 6 gauss. honeywell?s magnetic sensors are among the most sensitive and reliable low - field sensors in the industry. honeywell continues to maintain product excellence and performance by in troducing innovative solid - state magnetic sensor solutions. these are highly reliable, top performance products that are delivered when promised. honeywell?s magnetic sensor solutions provide real solutions you can count on. features benefits 4 surface mount 1 and 2 - axis sensors 4 easy to assemble & compatible with high speed smt assembly 4 low cost 4 designed for high volume, cost effective oem designs 4 4 - element wheatstone bridges 4 low noise passi ve element design 4 low voltage operations (2.0v) 4 compatible for battery powered applications 4 available in tape & reel packaging 4 high volume oem assembly 4 patented offset and set/reset straps 4 stray magnetic field compensation 4 wide field range ( up to +/ - 6 oe) 4 sensor can be used in strong magnetic field environments
hmc1001/1002/1021/1022 2 www.honeywell.com hmc1001/1002 s pecifications characteristics conditions* min typ max units bridge elements supply vbridge (vb) referenced to gnd - 5 .0 12 volts resistance bridge current = 10ma per bridge 600 850 1200 ohms operating temperature ambient - 55 150 c storage temperature ambient, unbiased - 55 175 c field range full scale (fs) ? total applied field - 2 +2 g auss linearity error best fit straight line 1 gauss 2 gauss 0.1 1.0 0.5 2.0 %fs hysteresis error 3 sweeps across 2 gauss 0.05 0.10 %fs repeatability error 3 sweeps across 2 gauss 0.05 0.10 %fs s/r repeatability outpu t variation after alternate s/r pulses vb = 5 v, i sr = 3 a 10 0 m v bridge offset offset = (out+) ? (out - ) field = 0 gauss after set pulse , vb = 8v - 60 - 15 +30 mv sensitivity set/reset current = 3 a 2.5 3.2 4.0 mv/v/gauss noise density @ 1hz, vb =5v 29 nv/sqrt hz resolution 10hz bandwidth, vb =5v 27 m gauss bandwidth magnetic signal (lower limit = dc) 5 mhz disturbing field sensitivity starts to degrade. use s/r pulse to restore sensitivity. 5 gauss sens itivity tempco t a = - 40 to 125c, vb=8 v t a = - 40 to 125c, ibridge=5ma - 0. 32 - 0. 30 - 0.06 - 0. 28 % /c bridge offset tempco t a = - 40 to 125c, no set/reset t a = - 40 to 125c, with set/reset 0.0 3 0.00 1 % /c bridge ohmic tempco t a = - 40 to 125c 0 .25 % /c cross - axis effect cross field = 1 gauss, happlied = 1 gauss with set/reset 3 0.5 %fs max. exposed field no perming effect on zero reading 10000 gauss set/reset straps resistance measured from s/r+ to s/r - 1 .5 1 .8 ohms current 0.1% duty cycle, or less, 2 m sec current pulse 2 .0 3. 0 5 amp resistance tempco t a = - 40 to 125c 0.37 % /c offset straps resistance measured from off+ to off - 2.5 3.5 ohms offset constant dc current fi eld applied in sensitive direction 46 51 56 ma/gauss resistance tempco t a = - 40 to 125c 0.39 % /c * tested at 25 c except stated otherwise.
hmc1001/1002/1021/1022 www.honeywell.com 3 hmc1021/102 2 s pecifications characteristics conditions* min typ max units bridge elements supply vbridge (vb) referenced to gnd 2 5.0 25 volts resistance bridge current = 10ma per bridge 8 00 1100 1 3 00 ohms operating temperature ambient - 55 150 c storage temperature ambient, unbiased - 55 175 c field range f ull scale (fs) ? total applied field - 6 + 6 gauss linearity error best fit straight line 1 gauss 3 gauss 6 gauss 0.05 0.4 1.6 %fs hysteresis error 3 sweeps across 2 gauss 0.0 8 %fs repeatability error 3 sweeps across 2 g auss 0. 08 %fs bridge offset offset = (out+) ? (out - ) field = 0 gauss after set pulse , vb = 5 v - 1 0 2.5 +11.25 mv sensitivity set/reset current = 0.5 a 0.8 1.0 1.25 mv/v/gauss noise density @ 1hz, vb=5v 48 nv/sqrt hz resoluti on 10hz bandwidth, vb=5v 85 m gauss bandwidth magnetic signal (lower limit = dc) 5 mhz disturbing field sensitivity starts to degrade. use s/r pulse to restore sensitivity. 20 gauss sensitivity tempco t a = - 40 to 125c, vb= 5 v t a = - 40 to 125c, ibridge=5ma - 0.32 - 0.30 - 0.06 - 0.28 % /c bridge offset tempco t a = - 40 to 125c, no set/reset t a = - 40 to 125c, with set/reset 0.0 5 0.00 1 % /c bridge ohmic tempco t a = - 40 to 125c 0.25 % /c cross - axis effect cross fie ld = 1 gauss, happlied = 1 gauss +0.3 %fs max. exposed field no perming effect on zero reading 10000 gauss set/reset straps resistance measured from s/r+ to s/r - 5.5 7.7 9 ohms current 0.1% duty cycle, or less, 2 m sec current pulse 0.5 0.5 4.0 amp resistance tempco t a = - 40 to 125c 0.37 % /c offset straps resistance measured from off+ to off - 38 50 60 ohms offset constant dc current field applied in sensitive direction 4.0 4.6 6.0 ma /gauss resistance tempco t a = - 40 to 125c 0.39 % /c * tested at 25 c except stated otherwise.
hmc1001/1002/1021/1022 4 www.honeywell.com key performance data
hmc1001/1002/1021/1022 www.honeywell.com 5 package / pinout specifications arrow indicates direction of applied field that generates a positive output voltage after a set pulse. basic device operation the honeywell hmc100x and hmc102x anisotropic m agneto - r esistive (amr) sensors are simple resistive wheatstone bridges to measure magnetic fields and only require a supply volta ge for the measurement . with power supply applied to the bridges, the sensors convert any incident magnetic field in the sensitive axis directions to a differential voltage outpu ts. in addition to the bridge circuits, each sensor has two on - chip magnetical ly coupled straps; the offset strap and the set/reset strap. these straps are honeywell patented features for incident field adjustment and magnetic domain alignment; and eliminate the need for external coils positioned around the sensors. the magnetoresi stive sensors are made of a nickel - iron (permalloy) thin - film deposited on a silicon wafer and patterned as a resistive strip element. in the presence of a magnetic field, a change in the bridge resistive elements causes a corresponding change in voltage a cross the bridge outputs.
hmc1001/1002/1021/1022 6 www.honeywell.com these resistive elements are aligned together to have a common sensitive axis (indicated by arrows on the pinouts) that will provide positive voltage change with magnetic fields increasing in the sensitive direction. because the output only is in proportion to the one - dimensional axis (the principle of anisotropy) and its magnitude, additional sensor bridges placed at orthogonal directions permit accurate measurement of arbitrary field direction. the combination of sensor bridges in two and three orthogonal axis permit applications such as compassing and magnetometry. see figure 1 for a representation of the magneto - resistive elements. figure 1 ? magneto - resistive wheatstone bridge elements the offset strap allows for several mod es of operation when a direct current is driven through it. these modes are: 1) subtraction (bucking) of an unwanted external magnetic field, 2) null - ing of the bridge offset voltage, 3) closed loop field cancellation, and 4) auto - calibration of bridge gai n. the set/reset strap can be pulsed with high currents for the following benefits: 1) enable the sensor to perform high sensitivity measurements, 2) flip the polarity of the bridge output voltage, and 3) periodically used to improve linearity, lower cros s - axis effects, and temperature effects. offset straps the offset strap is a spiral of metallization that couples to the sensor element?s sensitive axis. the offset strap has some modest resistance and requires a moderate current flow for each gauss of i nduced field. the straps will easily handle currents to b uck or boost fields through the linear measurement range, but designers should note the extreme thermal heating on the die when doing so. with most applications, the offset strap is not utilized and can be ignored. designers can leave one or both strap connections (off - and off+) open circuited. set/reset straps the set/reset strap is another spiral of metallization that couples to the sensor element ? s easy axis (perpendicular to the sensitive axi s on the sensor die ) . ea ch set/reset strap has a low resistance with a short but high required peak current for reset or set pulses. with rare exception, the set/reset strap must be used to periodically condition the magnetic domains of the magneto - resisti ve elements for best and reliable performance. a set pulse is defined as a positive pulse current entering the s/r+ strap connection. the successful result would be the sensor aligned in a forward easy - axis direction so that the sensor bridge?s polarity is a positive slope with positive fields on the sensitive axis result in positive voltages across the bridge output connections. a reset pulse is defined as a negative pulse current entering the s/r+ strap connection. the successful result would be the sens or aligned in a reverse easy - axis direction so that sensor bridge?s polarity is a negative slope with positive fields on the sensitive axis result in negative voltages across the bridge output connections. typically a reset pulse is sent first, followed b y a set pulse a few milliseconds later. by shoving the magnetic domains in completely opposite directions, any prior magnetic disturbances are likely to be completely erased by the duet of pulses. gnd permalloy thin film sensitive axis vb out - out+ easy axis gnd permalloy thin film sensitive axis vb out - out+ easy axis
hmc1001/1002/1021/1022 www.honeywell.com 7 for simpler circuits with less critical requirements for no ise and accuracy, a single polarity pulse circuit may be employed periodically (all sets or all resets). with these uni - polar pulses, several uni - polar pulses become close in performance to a single bipolar set/reset pulse circuit. noise characteristics the noise density curve for a typical amr sensor is shown in the figure below. the 1/f slope has a nominal corner frequency near 10hz and flattens out to a 3.8 nv/sqrthz slope. this is approximately equivalent to the johnson noise (or white noise) for an 850 ohm resistor, the typical bridge resistance. to relate the noise density voltage to the magnetic fields, use the following expressions: for vbridge = 5v and sensitivity = 3.2mv/v/gauss, the bridge output (voutput) is 16mv/gauss the noise density at 1 hz is about 30nv/sqrthz or 1.8 micro - gauss/sqrthz 1/f noise (0.1 to 10hz) = 30 * sqrt[(ln10/0.1)] nv = 64nv (rms) = 4 micro - gauss (rms) = 27 micro - gauss (pk - pk) white noise (bw = 1khz) = 3.8 * sqrt[bw] nv = 120nv (rms) = 50 micro - gauss (pk - pk)
hmc1001/1002/1021/1022 8 www.honeywell.com set/re set strap operation the reasons to perform a set or reset on an amr sensor are: 1) to recover from a strong external magnetic field that likely has re - magnetized the sensor, 2) to optimize the magnetic domains for most sensitive performance, and 3) to fli p the domains for extraction of bridge offset under changing temperature conditions. strong external magnetic fields that exceed a 10 to 20 gauss ?disturbing field? limit, can come from a variety of sources. the most common types of strong field sources c ome from permanent magnets such as speaker magnets, nearby high - current conductors such as welding cables and power feeder cables, and by magnetic coils in electronic equipment such as crt monitors and power transformers. magnets exhibit pole face strength s in hundreds to thousands of gauss. these high intensity magnetic field sources do not permanently damage the sensor e lements, but the elements will be disturbed to the exposed fields rather than the required easy axis directions. the result of this re - ma gnetizatio n of the sensor elements, the sensor will lack sensitivity or indicate a ?stuck? sensor output . using the set and reset pulses will magnetically ?restore? the sensor. amr sensors are also ferromagnetic devices with a crystalline structure. this same thin film structure that makes the sensor sensitive to external magnetic fields also has the downside that changing magnetic field directions and thermal energy over time will increase the self - noise of the sensor elements. this noise, while very smal l, does impair the accurate measurement of sub - milligauss field strengths or changes in field strength in microgauss increments. by employing frequent set and reset fields on the sensor, the self - noise will be to its lowest possible level. as the sensor e lement temperature changes, either due to self - heating or external environments, each element?s resistance will change in proportion to the temperature. one way to eliminate the bridge offset voltage is to make stable magnetic field measurements of the bri dge output voltage in between each set and reset field application. since the external field components of the bridge output voltage will flip polarity, the set and reset bridge output voltages can be subtracted and the result divided by two to calculate t he bridge offset. see application note an212 for the details on bridge offset voltage computation and correction. set/reset drive circuits the above description explained that providing pulses of electrical current creates the needed magnetic fields to r ealign the magnetic domains of the sensor resistive elements. also the rationale for performing these set and reset pulses has been justified. the following paragraphs shall show when and how to apply these pulsed currents, and circuits to implement them. figure 2 shows a simplistic schematic of a set/reset circuit. these set and reset pulses are shown in figure 2 as dampened exponential pulse waveforms because the most popular method of generating these relatively high current, short duration pulses is vi a a capacitive ?charge and dump? type of circuit. most electronics, especially in consumer battery powered devices, do not have the capability to supply these high current pulses from their existing power supply sources. thus ?vsr? is actually a charged up capacitor that is suddenly switched across the set/reset strap. the value of this capacitor is usually a couple hundred nano - farads ( h f) to a few micro - farads ( m f) depending on the strap resistance to be driven. the decay of the exponential waveform will mostly be governed by a time constant ( t or tau) that is the capacitance in farads multiplied by the resistance, and is measured in se conds. figure 2 ? a simple set/reset circuit 1 vsr rsr 5 iset ireset strap resistance set/reset pulse source s/r+ s/r - t = r*c = ~2 m sec 1 vsr rsr 5 iset ireset strap resistance set/reset pulse source s/r+ s/r - t = r*c = ~2 m sec
hmc1001/1002/1021/1022 www.honeywell.com 9 the next circuit implementation is the classic set/reset design in which a push - pull output stage (totem pole stage) drives one end of the hmc1001 set/reset strap, with the other end grounded. f igure 3 shows this circuit. figure 3 ? totem pole set/reset circuit for hmc1001 the totem pole moniker comes from the stacked semiconductors between the positive supply voltage (vdd ) and the negative connection (ground). in the above example circuit, the semiconductors depicted are two complementary power mosfets, with the p - channel device on top and the n - channel device on the bottom. th e international rectifier irf7105 part is chosen in this circuit as it contains both p - chann el and n - channel mosf et die in a very small package, and has the electrical characteristics needed for this circuit. other manufacturers can be used as well with the requirements that they can be fully turned on/off with a 5 - volt logic stimulus, handle the peak set/reset strap load currents, and present an ?on? resistance at those peak currents th at is fairly small in comparison to the connected strap load resistance. higher voltage totem pole circuits while the previous example uses the convenience o f st andard 5 - volt logic drive and modest supplies , many sensor designs require higher applied voltages to the set/reset straps to achieve greater currents or because the straps are series connected to assure even current distribution across all the straps puls ed. by creating series chains of straps, variances in strap resistance are less likely to fall out of the minimum or maximum range for peak pulse currents. if the straps are parallel connected, wide set/reset stra p ohmic tolerances may be prone to ?current hogging? and the straps will provide dissimilar magnetic fields at each sensor, potentially creating non - uniform accuracies at each sensor axis. the circuit in figure 3 relies on mosfets that could predictably be turned off and on completely using logic level inputs. at higher voltages, the p - channel device needs its gate drive voltage to approach the source voltage, which is higher than usual logic levels. to perform this level shifting from logic levels to higher pulse source voltage supply levels, a bj t level shifter sub - circuit is employed to perform this task. figure 4 shows this higher voltage operating circuit. from figure 4, rsr1, rsr2, and rsr3 are three strap resistances that are modeled from the hmc1001 or hmc1002 products. three of these strap resistances are chosen since many users desire 3 - axis magnetic field sensing that comes from a pairing of a hmc1001 and a hmc1002. also this combination of three series straps is also used on the hmc2003 hybrid sensor module and in the hmr2300 smart digit al magnetometer. x1 irf7105p x2 irf7105n c1 10u r1 200 c2 0.47u rsr 1.5 vdd c3 0.47u r2 22k c4 0.1u vsource vsr rsource 10 8 volts x1 irf7105p x2 irf7105n c1 10u r1 200 c2 0.47u rsr 1.5 vdd c3 0.47u r2 22k c4 0.1u vsource vsr rsource 10 8 volts
hmc1001/1002/1021/1022 10 www.honeywell.com figure 4 ? higher voltage set/reset circuit for hmc1001 & hmc1002 the three strap resistances are chosen at 1.8 ohms, or the worst - case high resistance points. since they require a minimum of 3 amperes peak, the series combination requires at least 16.2 volts, so a circuit vdd of about 18 volts would about the right level to drive the strap load and allocate for losses in the c1 capacitor esr and the mosfet switches x1 and x2. c1?s value is also chosen at 0.22 micro - farad so the circuit time constant is at least around 1 micro - second. supply reservoir capacitor c2 is chosen to many times the value of c1 and is also picked for small size, working voltage, and low esr relative to the strap load resistance. c2 ty pically will be in the 1 to 10 micro - farad range and best to error on the high capacitance side since c2 now supplies additional x1 gate drive circuitry. resistor r5 is then chosen after c2 to set the recharge time constant and to limit peak supply current . these capacitors should be chosen to have a low esr characteristic of around 0.2 ohms per capacitor. working backwards from the strap load resistance, mosfets x1 and x2 are chosen as irf7105 due to the total packaged size (both x1 and x2 in one soic - 8), and meeting the requirements for operating voltages, peak currents, and low on resistances. x2 is directly driven from digital logic denoted as ?vset?, and ?vreset? drives the level shifting sub - circuit to x1. note that vreset turns off x2 first prior to x1 being driven on by vset, and also x1 is turned off before x2 is turned on. while one logic line could control the operation of vset and vreset, the additional inverter stages and pulse delay components may be too space and cost consuming compared to two logic ports in a microcontroller. see figure 4 in application note 201 for the discrete vset and vreset pulse forming circuit. transis tors q1 and q2 in figure 4 are chosen to be generic bjts to force mosfet x1?s gate charge quickly into on and off states . resistors r1 and r2 are selected as nominal 1000 ohm values that can pump or dump x1?s gate charge by supplying q1 and q2 with enough base drive currents to flip their on and off states. transistor q3 is also chosen as a generic, but reasonably fast swit ch transistor to perform the level shift function with resistors r1 and r2. components r3, c3 and d1 are chosen to properly drive q3 from a logic level source, with c3 and d1 denoted as a ?speed - up? network to quickly switch q3 within a few nanoseconds of logic transitions . 5 1 2 x1 irf7105p 8 x2 irf7105n 3 q1 2n2222 q2 2n2907 r1 1000 4 r2 1000 6 q3 2n2222 7 r3 1000 10 vdd vset vreset 12 rsr3 1.8 9 c1 0.22u c2 10u r5 220 c3 1n d1 1n4148 11 rsr1 1.8 rsr2 1.8
hmc1001/1002/1021/1022 www.honeywell.com 11 application circuits the following are typical application circuits using the hmc100x and hmc102x sensors. two axis compass or magnetometer figure 5 shows the typical schematic diagram. figure 5 ? 2 - axis compass or magnetometer from figure 5, the typical power supplied for vdd is nominally 5 volts, with about 8 volts for the set/reset strap supply (vsr). a pair of complementary power mosfets provides the electronic switch functions, driving the se t/reset minus pins with the set/reset plus pins returned to the mosfet ground. the mosfets are driven by typical 5 volt logic with normally high levels expected when not pulsing. each logic transition creates a very high current pulse, as high - to - low tran s i tions turn - on the p - channel fet while turning - off the n - channel fet. this transfers some of the energy from the 10uf reservoir capacitor to the pair of 0.47uf capacitors while providing a positive pulse. a negative pulse is performed on the low - to - high lo gic transi tion as the p - channel fet is turned off and the n - channel fet is turned on. then the energy from the pair of 0.47uf capacitors is discharged through the set/reset straps and the n - channel mosfet. ceramic capacitors with a low - esr characteristic a re required for best pulse performance. since the sensor output difference voltage is amplified by low cost operational amplifiers with a low supply voltage feature (lmv324n), the amplifier require s a half supply voltage reference (vref). this reference v oltage is form ed via a buffered rail - splitter circuit, using a spare op - amp and resistors. the 1 nano - farad capacitors are used to bandwidth limit the sensor, and to suppress interference. the resistors around the op - amp are chosen for earth?s magnetic fie ld strength (about 0.6 gauss) levels and to match with the sensor impedance. the 4.99k - ohm resistors are a bridging impedance that is normally chosen to be 4 to 10 times larger than the sensor bridge resistance elements (hmc1002) at 850 ohms. the 1 r1 850 2 r2 850 r3 850 r4 850 vcc vee 4 3 6 x1a lmv324n r5 4.99k r6 4.99k r7 360k c1 1n vdd vdd r8 360k vref 8 r9 850 9 r10 850 r11 850 r12 850 vcc vee 10 11 12 x1b lmv324n r13 4.99k r14 4.99k r15 360k c2 1n vdd vdd r16 360k vref 16 r17 1.5 r18 1.5 xout yout vcc vee 15 x1c lmv324n vdd r19 1k r20 1k vdd vref c3 0.1u 17 18 14 x2 irf7105p c4 10u x3 irf7105n c5 0.47u c6 0.47u 13 r21 100 sr_in vsr hmc1002 1 r1 850 2 r2 850 r3 850 r4 850 vcc vee 4 3 6 x1a lmv324n r5 4.99k r6 4.99k r7 360k c1 1n vdd vdd r8 360k vref 8 r9 850 9 r10 850 r11 850 r12 850 vcc vee 10 11 12 x1b lmv324n r13 4.99k r14 4.99k r15 360k c2 1n vdd vdd r16 360k vref 16 r17 1.5 r18 1.5 xout yout vcc vee 15 x1c lmv324n vdd r19 1k r20 1k vdd vref c3 0.1u 17 18 14 x2 irf7105p c4 10u x3 irf7105n c5 0.47u c6 0.47u 13 r21 100 sr_in vsr hmc1002
hmc1001/1002/1021/1022 12 www.honeywell.com 360k - ohm feedback and reference resistors are chosen to provide a nominal 230mv/v/gauss gain characteristic or 1.15v/gauss gain with vdd at 5 volts. other values than 360k - ohms may be chosen; with smaller resistances for larger fields and larger resistances for low er field strengths. be aware that sensor bridge offsets factor into the signal gain selection as the offsets may be as large as the signal to be measured. see application note an212 on methods to handle bridge offset voltages. as a magnetometer, the circu it outputs ( xout and yout ) should be measured against vref and scaled for 1.15 volts per gauss using a 5 volt sensor/amplifier power supply (vdd). since the sensor?s bandwidth is 5 mhz, the sampling rate of the outputs can be very fast, to the point were t he filtering and speed of the amplifiers begins to effect the measurements. resolution will be mostly to the size of the analog - to - digital converter (adc), where a 10 - bit adc would spread its 1024 counts across the power supply or tighter. as a compass , t he two outputs constrain the earth?s magnetic field measurement to horizontal orientations with the xout and yout feeding the heading equation of arctan (yout/xout) in degrees. the xout direction of the hmc1002 should be mounted to the forward direction of the product for proper orientation. if a tilt - compensated compass is desired, a third axis could be made from the spare lmv324n amplifier and a hmc1001 sensor. refer to the technical papers on compassing from the website for more detail on compass impleme ntation. field detector or current sensor a simple sensor implementation is shown in figure 6 for a single axis sensor and signal conditioning circuitry for detecting a magnetic disturbance, or as a current sensor when placed near a current carrying cond uctor. for more details on current sensing, see application note an209 on the website. from figure 6, the hmc1021 sensor s are different from the hmc100x parts in that the bridge resistances increase to 1100 ohms and the set/reset strap resistance increase s to 4.5 ohms. because the minimum set/r eset peak current is down to 0.5 amperes, the set/reset drive circuit can now be run at common supply rails of 5 or 3 volts (vdd). due to the increased resistance of the set/reset strap, capacitor c3 can be reduced t o about 0.22uf to maintain the desired 1 to 2 microsecond time constant. capacitor c2 is typically chosen to be about ten times the series capacitor value, or 2.2uf. the same pulse transition scheme in figure 5 applies to figure 6. the sensor/amplifier ci rcuit is likewise similar but the 1mv/v/gauss sensitivity requires a gain boost by increasing feedback/reference resistors for sensing low fields like earth?s magnetic field. if a 2 or 3 - axis compass is to be designed with the hmc102x series sensor, parts like the hmc1022 plus the hmc1021z can be used, with replication of the difference amplifier stages for each axis. by choosing the 1 meg - ohm and 4.99k - ohm resistors, the gain with a 5 volt supply produces about a 1v/gauss transfer characteristic and center ed at half supply (2.5 volts). an instrumentation amplifier could be substituted for the operational amplifier to minimize external discrete components, but the very low cost of op - amps like the lmv741/lmv358/lmv324 family is hard to beat if price is mor e important than printed circuit board footprint. the signal output of the amplifier can be directly placed on the input of an adc and further processed in digital form. if the adc range spans the power supply range, then a 10 - bit adc can have count 512 of 1024 used as the zero gauss point when the output rests at half - supply. if 3 volt operation is required, the designer can substitute the irf7507 part for the irf7105 for 2.7 volt logic drive of the complementary mosfet gates.
hmc1001/1002/1021/1022 www.honeywell.com 13 figure 6 ? field detector or current sensor mounting considerations stencil design and solder paste a 4 mil stencil and 100% paste cover age is recommended for the electrical contact pads. pick and place placement is machine dependant and no re strictions are recommended. reflow and rework no special pro file is required for the hmc10xx parts . the product is compatible with lead and no - lead eutectic solder paste reflow profiles. honeywell recommends the adherence to solder paste manufa cturer?s g uidelines. the sensors may be reworked with soldering irons, but extreme care must be taken not to overheat the part?s circuit board pads . irons with a tip temperature no greater than 315 c should be used. excessive rework risks the copper pads pulling awa y into the molten solder. 1 r1 1.1k 2 r2 1.1k r3 1.1k r4 1.1k vcc vee 4 3 6 x1a lmv324n r5 4.99k r6 4.99k r7 1meg c1 1n vdd vdd 8 r8 1meg 16 r12 4.5 xout r9 10k 17 18 14 x2 irf7105p c2 2.2u x3 irf7105n c3 0.22u r11 200 sr_in vdd r10 10k vdd hmc1021 1 r1 1.1k 2 r2 1.1k r3 1.1k r4 1.1k vcc vee 4 3 6 x1a lmv324n r5 4.99k r6 4.99k r7 1meg c1 1n vdd vdd 8 r8 1meg 16 r12 4.5 xout r9 10k 17 18 14 x2 irf7105p c2 2.2u x3 irf7105n c3 0.22u r11 200 sr_in vdd r10 10k vdd hmc1021
hmc1001/1002/1021/1022 14 www.honeywell.com package outlines
hmc1001/1002/1021/1022 www.honeywell.com 15 ordering information ordering number product packaging hmc1001 one axis magnetic sensor, 8 - pin sip esd tubes hmc1002 hmc1002 - tr two axis magnetic sens or, 20 - pin soic esd tubes 1,000 tape & reel hmc1021s hmc1021s - tr one axis magnetic sensor, 8 - pin soic esd tubes 1,000 tape & reel hmc1021z one axis magnetic sensor, 8 - pin sip esd tubes hmc1022 hmc1022 - tr two axis magnetic sensor, 16 - pin soic cut tape 2, 500 tape & reel * when ordering the ? rc in the product part number represents rohs compliant. this labeling is temporary during the transition period from leaded to non - leaded parts. find out more for more information on honeywell?s magnet ic sensors visit us online at www.magneticsensors.com or contact us at 800 - 323 - 8295 (763 - 954 - 2474 internationally). the application circuits herein constitute typical usage and interface of honeywell product. honeywell does not warranty or a ssume liabil ity of customer - designed circuits derived from this description or depiction. honeywell reserves the right to make changes to improve reliability, function or design. honeywell does not assume any liabil ity arising out of the application or use of any pr oduct or circuit described herein; neither does it convey any license under its patent rights nor the rights of others. u.s. patents 4,441,072, 4,533,872, 4,569,742, 4,681,812, 4,847,584 6,529,114 and 7,095,226 apply to the technology describe d honeywell 12001 highway 55 plymouth, mn 55441 tel: 800 - 323 - 8295 www.honeywell.com/magneticsensors form #900 248 rev c au gust 2008 ?200 8 honeywell international inc.

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